Each - Draper Laboratory
Each - Draper Laboratory
Each - Draper Laboratory
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= damping<br />
k = stiffness. Mostly mechanical with modifications<br />
by electrostatic forces<br />
kds = quadrature coupling. The drive axis suspension<br />
force coupling into the sense axes<br />
bds = in-phase damping ‘surfboard’ coupling to sense<br />
axis<br />
x = motion along drive axis (parallel to substrate)<br />
y = motion along sense axis (normal to substrate)<br />
s = Laplace transform of d /dt<br />
Fd = motor drive force applied by the outer combs in<br />
Figure 1<br />
WI = slowly varying input rate<br />
a = drive force coupling to sense axis<br />
Q = quality factor<br />
From (2) and (3), another challenge emerges. The driving<br />
force as well as the drive axis suspension force and drive<br />
axis damping are coupled into the sense axis. With good<br />
design, these forces should be small compared with the<br />
Coriolis Force .<br />
For low-frequency angular rate inputs, the desired output<br />
is the angular rate modulated by the drive frequency. As<br />
shown in the electrical circuit of Figure 3, the proof masses<br />
are the negative input of a high input impedance, highgain<br />
operational amplifier whose input node is at virtual<br />
ground. The feedback resistor is large so that it does not<br />
affect the output at the gyro’s drive frequencies. From (3)<br />
and Figure 3, the preamplifier output is given by (Appendix<br />
B):<br />
where<br />
Vo = output of preamplifier<br />
Vs = bias voltage (plus and minus applied to right and<br />
left sense plates in Figure 1) on sense electrodes<br />
(5 V, example values are given in parentheses)<br />
Vc = coupling (drive feedthrough)<br />
VN = preamplifier input voltage noise (10-8 V/ )<br />
46 Error Sources in In-Plane Silicon Tuning-Fork MEMS Gyroscopes<br />
(4)<br />
Cfb = feedback capacitor about the sense axis preamplifier<br />
(2 pF)<br />
Cs = total of sense capacitors (2 pF)<br />
CN = preamplifier input capacitance to ground (5<br />
pF)<br />
Cc = coupling (undesirable capacitor) to virtual<br />
ground (preamplifier input)<br />
dCs /dy = differential change of sense capacitors with y<br />
motion (2 pF/3 µm)<br />
SC = sum of all capacitors attached to the virtual<br />
ground. Includes strays, working, feedback,<br />
and amplifier capacitors (12 pF).<br />
wd = drive mode undamped natural frequency<br />
(20 kHz x 2 prad/s)<br />
w s = sense mode undamped natural frequency<br />
(22 kHz x 2 prad/s)<br />
x o = amplitude of drive motion (10 µm zero-to-peak)<br />
Fs = cross coupling forces acting along the sense<br />
direction (B-6)<br />
q = phase shift through sense dynamics (B-6)<br />
Proof<br />
Mass<br />
C c Cs/2 C s /2<br />
V c -V s V s<br />
C N<br />
Figure 3. Circuit diagram for sense preamplifier analysis.<br />
In (4), it is assumed that the proof mass motion is driven<br />
so that the displacement is a sinusoidal function of time.<br />
The rate signal, the Coriolis term, is in phase with the<br />
proof mass velocity, i.e., in quadrature with the proof mass<br />
position. For the sample parameters above, the gyro scale<br />
factor at the preamplifier output is 1.3 mV/rad/s. With a<br />
field effect transistor (FET) preamplifier whose input noise<br />
at drive frequency is 10 nV/ , the rate equivalent noise<br />
is 10 deg/h/ . Attaining the theoretical noise limit is a<br />
challenge discussed further in the “Electrical Coupling”<br />
section.<br />
Because of the sense-drive frequency separation and high<br />
sense-axis quality factor, the damping term is omitted in<br />
the denominator of (4); therefore, gain does not depend<br />
on damping. High resonant frequencies are desired to<br />
remove the gyro’s sensitive frequencies from acoustic<br />
noise and vibration and to permit isolators that allow<br />
adequate bandwidth. For a fixed sense-plate bias, higher<br />
sensitivity is achieved by lowering the resonant frequencies<br />
and/or by decreasing the separation between sense<br />
and drive mode. Drive frequencies of 10-25 kHz and<br />
sense-drive mode separations of 5-15% have worked well<br />
for MEMS TFGs. At baseband, the transfer function of<br />
output voltage to rate input has a lightly damped peak<br />
at the frequency separation. Placing the separation at 1-2<br />
kHz allows a 100-Hz bandwidth, which adequately filters<br />
R fb<br />
V N<br />
C fb<br />
–<br />
+<br />
V R<br />
V o<br />
Output<br />
Voltage