obtainof the reduced system,wherewith[ M ] [ U][ ][ V]1H= Σ , (16)[] Σ = Diag ⎡s() ! s() r e( r + )!e( N + )⎣1, , , 1, , 1 ⎤⎦,() ( ) () ( ) ( )s 1 ≥ s 2 ≥…≥ s r ≥ e r+ 1 ≥…≥ e N + 1 ≥0.V are the right and the, respectively. It is assumed1 has r dominant singular values and the remaining1+ N -rsingular values are close to zero and are considerednoise. So, if ⎡⎣M1 ( N + 1, N + 1)⎤⎦ has an effective rank r,then all the singular values ei () should be zero. When thesingular values ei () are small nonzero values, the rank of[ M 1]is not too far from r. The second step consists ofrearranging (16) such thatThe orthogonal matrices [ U ] and [ ]left singular vectors of [ M 1]that [ M ]where[ ]M ⎣U⎦⎣V⎦1 = ⎡ ⎤⎡ ⎤,[ U][ ] 1/2and 1/2⎡V⎤=Σ[] [] V .⎡⎣U⎤= ⎦ Σ⎣⎦(17)Finally, ⎡⎣U⎤⎦ and ⎡ ⎣ V ⎤ ⎦ are used to obtain the filtered statespacematrices[ A r], [ B r], and[ C r]. Specifically, thereduced state-space matrices are[ A ] = ⎡U1⎤ ⎡U2⎤=⎡V1⎤ ⎡V2 ⎤ ,r+ +⎣ ⎦ ⎣ ⎦ ⎣ ⎦ ⎣ ⎦[ B ]r[ C ]r= ⎡⎣V⎤⎦= ⎡⎣U⎤⎦(1),(1),(18)(19)(20)where⎡⎣U 1 ⎤⎦is the first N block rows and the first r columnsof ⎡⎣U⎤⎦ , ⎡⎣U 2 ⎤⎦ is the last N block rows and the first r columnsof ⎡⎣U⎤⎦ , ⎡⎣V 1⎤⎦is the first r rows and the first N block columnsof ⎡⎣V⎤⎦ , V 2 ⎤⎦is the first r rows and the last N block columnsof ⎡⎣V⎤⎦ , () i⎡⎣U⎤⎦ is the ith block row and the first r columnsof ⎡⎣U⎤⎦ , () i⎡⎣V⎤⎦ is the first r rows and the ith block columnof ⎡⎣V⎤⎦ Ḃy using these state-space matrices, one can generatethe impulse response h and the system transfer function Hk() [ ][ ][ ] 1 ,h k = C A B −(21)−1() [ ][ ] [ ]H z = C zI − A B , (22)r r r rwhere I r is the r× r identity matrix. The n poles z m of thereduced system ( 1 ≤m≤ n)are the eigenvalues of the statematrix [ A r]and correspond to the damping coefficientsand the frequencies in the s domain through the relationship( m j m)Tsm = +(23)z e α ωThis concludes the overview of how the poles are computedin the state-space approaches. Once the poles are obtainedthe residues can be obtained using (12).4. State-Space Approach 2(SS2) with Extended ImpulseResponse Grammian (EIRG)Similar to section 3, consider a stable, linear, timeinvariant,discrete-time, single-input and single-outputsystem of degree n described by the minimal realizationx( k + ) = [ A] x() k + [ B] u()k() = [ ] ⎡ () ⎤.⎡⎣ 1 ⎤⎦ ⎡⎣ ⎤⎦,y k C ⎣x k ⎦The Extended Impulse Response Grammian [ P ]N for a system of degree n is defined as[ P ]NN(24)of order⎡ H H Hhk+ 1hk+ 1 hk+ 1hk+ 2 " hk 1h⎤+ k+N⎢⎥∞ H H H⎢hk+ 2hk+ 1 hk+ 2hk+ 2 " hk+ 2hk+N ⎥= ∑ ⎢ ⎥k=0 ⎢ # # # ⎥⎢ H H Hhk+ Nhk+ 1 hk+ Nhk+ 2 hk+ Nh⎥⎣" k+N⎦(25)for each positive integer N and for every n≤N , whereand { }kk−1[ ][ ] [ ]h = C A B(26)h k is a set of Markov parameters or an impulseresponsesequence. The infinite sum of matrices in (25)exists when the impulse response is stable. In this case, thesummation is equivalent to the matrix of element-wisesummations. Analogous to the decomposition of [ M 1]in(16), the SVD of the Extended Impulse Response Grammian(EIRG) is30The<strong>Radio</strong> <strong>Science</strong> <strong>Bulletin</strong> No <strong>313</strong> (<strong>June</strong>, <strong>2005</strong>)
whereH[ P ] [ U][ ][ V] ,N= Σ (27)[] Σ = Diag ⎡s() s( )! s() r e( r + )!e( N )with⎣1, 2, , 1, , ⎤⎦,() ( ) () ( ) ( )s 1 ≥ s 2 ≥…≥ s r ≥ e r + 1 ≥…≥e N ≥0.As noted earlier, the singular values { e( r + 1 ),!,e( N)}should be zero if the matrix [ P N ] has rank r, and the rankof [ P ] is approximately r when the remaining singularNvalues are very small. Definewhere [ ] j[ ]1 H( ) 4 1[] 4 [ ][ ] [ ][ ]X ≡ U Σ = Σ Ur≡ ⎡ , , ⎤,1 ⎢ ⎣⎥ ⎦2 r 1X ≡ ⎡ X , , X + ⎤,2 ⎢ ⎣⎥ ⎦1[ X] [ X] " [ X][ ] [ ] " [ ]H,(28)X is the jth column block of the matrixX truncated to the first r elements. Although the form of(27) is the same as (5) and (16), the decomposition in (28)differs from (18).In this case, the reduced state matrices [ A r], [ r]and [ C r]are given by[ A ] = [ X ][ X ]+ if and only if[ r][ ]r(1)2 1[ B ] [ X] 1 ,r1 2B ,A X = [ X] ,(29)= (30)−[ U][ ] 1/4 ,⎡C ⎣⎤=⎦Σ(31)[ C ]r(1),= ⎡C ⎣⎤(32)⎦where ⎡C ⎣⎤⎦is the ith block row of matrix [ C ] truncatedto the first r elements. If the reduced state-spacematrices[ A r], [ B r], and [ C r]are known, then the poles ofthe system can be extracted using the outlined procedure forSS1.5. Computation of Poles forTemporal Scattered FieldIn this study, the temporal back-scatteredelectromagnetic fields from five objects are used as impulseresponsesequences for the three direct-data-domain methods(MPM, SS1, SS2). To obtain the simulated scattered fieldsin the time domain, the frequency-domain back-scatteredfields are first calculated with WIPL-D [15], a method-ofmomentscode. WIPL-D uses an electric field integralequation (EFIE) for conducting structures and the PMCHW(Poggio-Miller-Chang-Harrington-Wu) Equation forcomposite structures. The time-domain data is calculatedby computing the inverse Fourier transform of the frequencydomainresult. Before taking the inverse Fourier transformof the frequency domain data, a Gaussian window is appliedto limit the bandwidth of the simulations.The advantages of the Gaussian window are two fold:(1) it provides a smooth roll off in time and frequency; and(2) it is well suited for numerical computation, as it generatesessentially band-limited frequency-domain data. Theexpression for this window in the time domain is [16]with()g t=σ1e2−a( − ),(33)ct ctγ = 0 .(34)σThe parameter c is the speed of light in free space, t 0 is atime delay that represents the peak time shift from theorigin, and σ is the pulse width that can be defined so thatthe peak value has dropped to about 2% at time t forct -ct0=± 2σ. Figure 1(a) shows an example of thetemporal Gaussian pulse, where σ = 1.0 and lm. The unitlm denotes a light meter, which is the length of time for anelectromagnetic wave to travel 1m. When the medium isfree space, 1lm = 3.33564ns. Since the Fourier transform ofa Gaussian function is Gaussian, the Fourier transform of(33) is( )πσ f 21 −( )c − j2πf t=0 (35)G f e ecand the frequency band corresponding to the pulse width isplotted in Figure 1(b).To illustrate the three fundamental data types (smooth,rapidly fluctuating, noise-like), five geometrically simpleobjects are analyzed: a thin conducting wire, a perfectlyconducting sphere, a perfectly conducting finite closedcylinder, a dielectric sphere, and a composite metallicdielectricsphere.5.1 Thin Conducting WireThe first example is a thin-wire scattering element of,The<strong>Radio</strong> <strong>Science</strong> <strong>Bulletin</strong> No <strong>313</strong> (<strong>June</strong>, <strong>2005</strong>) 31
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