an investigation of dual stator winding induction machines

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[10.37]. M. Rashed P. F. A. MacConnell and A.F. Stronach, “Nonlinear adaptive statefeedback speed control of a voltage-fed induction motor with varying parameters,” IEEE Transactions on Industry Applications, Vol. 42, No. 3, pp. 723–732, May/Jun. 2006. [10.38]. M. Hasegawa, “Robust-adaptive-observer design based on γ-positive real problem for sensorless induction-motor drives,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 76–85, February 2006. [10.39]. G. Dong, "Sensorless and efficiency optimized induction machine control with associated converter PWM modulation schemes,” Ph.D dissertation, Tennessee Technological University, Cookeville, TN, 2005. [10.40]. M. Depenbrock and C. Evers, “Model-based speed identification for induction machines in the whole operating range,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 31–40, February 2006. [10.41]. M. Boussak and K. Jarray, “A high-performance sensorless indirect stator flux orientation control of induction motor drive,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 41–49, February 2006. [10.42]. C. Lascu, I. Boldea and F. Blaabjerg, “Direct torque control of sensorless induction motor drives: A sliding-mode approach,” IEEE Transactions on Industry Applications, Vol. 40, No. 2, pp. 582–590, Mar./Apr. 2004. [10.43]. J. Li, L. Xu and Z. Zhang, “An adaptive sliding-mode observer for induction motor sensorless speed control,” IEEE Transactions on Industry Applications, Vol. 41, No. 4, pp. 1039–1046, Jul./Aug. 2005. [10.44]. M. Rashed, K. B. Goh, M. W. Dunnigan, P. F. A. MacConnell, A.F. Stronach and B. W. Williams, “Sensorless second-order sliding mode speed control of a voltage-fed induction-motor drive using nonlinear state feedback,” IEE Proceeding – Electrical Power Applications, vol. 152, no. 5, pp. 1127–1136, September 2005. [10.45]. G. Edelbaher, K. Jezernik and E. Urlep, “Low-spees sensorless control of induction machine,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 120-129, February 2006. [10.46]. M. Comanescu and L. Xu, “Sliding-mode MRAS speed estimations for sensorless vector control of induction machine,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 146-153, February 2006. [10.47]. C. Lascu, I. Boldea and F. Blaabjerg, “Very-low-speed variable-structure control of sensorless induction machine drives without signal injection,” IEEE Transactions on Industry Applications, Vol. 41, No. 2, pp. 591–598, Mar./Apr. 2005. 458
[10.48]. K. Lee and F. Blaabjerg, “Reduced-order extended Luenberger observer based sensorless vector control driven by Matrix converter with nonlinearity compensation,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 66-75, February 2006. [10.49]. M. Cirrincione and M. Pucci, G. Cirrincione and G. Gapolino, “An adaptive speed observer based on a new total least-squares neuron for induction machine drives,” IEEE Transactions on Industry Applications, Vol. 42, No. 1, pp. 89-104, Jan./Feb. 2006. [10.50]. M. Comanescu and L. Xu, “An improved flux observer based on PLL frequency estimator for sensorless vector control of induction motors,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 50-56, February 2006. [10.51]. K. Ide, J. Ha and M. Sawamura, “A hybrid speed estimator of flux observer for induction motor drives,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 130-137, February 2006. [10.52]. R. Cardenas and R. Pena, “Sensorless vector control of induction machines for variable-speed wind energy application,” IEEE Transactions on Energy Conversion, Vol. 19, No. 1, pp. 196-205, March 2004. [10.53]. R. Cardenas, R. Pena, J. Proboste, G. Asher and J. Clare, “MRAS observer for sensorless control of standalone doubly fed induction generator,” IEEE Transactions on Energy Conversion, Vol. 20, No. 4, pp. 710-718, December 2005. [10.54]. G. Poddar and V. T. Ranganathan, “sensorless double-inverter-fed wound-rotor induction-machine drive,” IEEE Transactions on Industrial Electronics, Vol. 53, No. 1, pp. 86-95, February 2006. [10.55]. L. Kreindler, J. C. Moreira, A. Telsa and T. A. Lipo, “direct field orientation using the stator phase voltage third harmonics,” IEEE Transactions on Industry Applications, Vol. 30, No. 2, pp. 441–447, Mar./Apr. 1994. [10.56]. M. D. Manjrekar, T. A. Lipo, S. Chang and K. Kim, “Flux tracking methods for direct field orientation,” International Conference on Electrical Machines, Turky, pp. 1022-1029, Sep. 1998. [10.57]. J. Ha and S. Sul, ” Sensorless field-orientation control of an induction machine by high-frequency signal injection,” IEEE Transactions on Industry Applications, Vol. 35, No. 1, pp. 45–51, Jan./Feb. 1999. [10.58]. N. Teske, G. M. Asher, M. Sumner and K. J. Bradley, “Encoderless postion estimation for symmetric cage induction machines under loaded conditions,” IEEE Transactions on Industry Applications, Vol. 37, No. 6, pp. 1793–1800, Nov./Dec. 2001. 459
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AN ABSTRACT OF A DISSERTAION AN INV
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coupling and interaction terms are
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CERTIFICATE OF APPROVAL OF DISSERTA
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ACKNOWLEDGEMENTS I would like to ex
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vi Page 2.2 Machine Design I.......
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viii Page 4.2.3 Self Inductances of
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x Page 7.3.4 f = 30 Hz and f = 95 H
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xii Page 10.8 D-decomposition Metho
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LIST OF FIGURES xiv Page Figure 1.1
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Figure 3.10 The simulation of the s
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Figure 3.34 Measured flux densities
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xx Page Figure 4.8 Self-inductance
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Figure 5.2. Simulation results for
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Figure 6.8. The dynamic response of
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Figure 7.22. Copper losses of the m
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Figure 8.7. The dynamic response of
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Figure 9.4 Steady state analysis, (
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Figure 9.12. The steady state wavef
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xxxiv Page Figure 10.16 Pole-zero m
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Figure 11.2 Per phase equivalent ci
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CHAPTER 1 INTRODUCTION AND LITERATU
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The last is the recently developed
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It should be noted that at any time
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A. R. Munoz and T.A. Lipo are pione
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has to be modified to adapt to thes
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circuit model of an induction machi
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ωr stator rotor 13 ωr rotor (a) (
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1.2.4 Field Analysis Method In [5.1
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separated dc source, etc. From the
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in [8.14]. In [8.15-8.17], the stud
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[8.22] and the total losses of the
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proposed. The switching frequency i
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The actual rotor mechanical speed i
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1.2.9 Induction Machine Drive---Vec
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stator windings were used as flux s
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The rotor flux can be obtained by:
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The basic idea of a closed loop flu
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estimation. It has been claimed in
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{ k [ ˆ* ( i iˆ ) ] ( k) [ ˆ* Im
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integral and a new stretch-turn ope
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The most recent overview paper is g
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CHAPTER 2 DUAL STATOR WINDING INDUC
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Table 2.1 Parameters of machine des
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A C B 2.2.2 Air Gap Flux Density X
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where, ω s1 and s2 respectively.
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There are two unknown variables in
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Since small machines typically have
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N s E = (2.18) 4. 44 fK φ 1 m Flux
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conduct away the heat produced in t
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k cs τ s = 2 2b ⎪ ⎧ ⎡ ⎤⎪
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are: Fts = H ts( ave) d s ( ave) =
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1 2 1 = H o ( ) + H o ( ) + H cr 90
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The skew of the stator winding is n
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0 bs Figure 2.5. Detailed stator sl
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y: The pole pitch at the mid point
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L lsk = L m ( α 2) ⎪⎧ ⎡sin
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2.3.4 Rotor Bar Resistance r b The
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2.3.7 Rotor Resistance Referred to
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Substituting δ = π into (2.97) an
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atio also increases. The air gap fl
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From (2.105-2.108), the ratio of th
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2.5 Conclusions In this chapter, a
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A recently developed dual stator wi
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stator winding induction machine ba
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∫ H ⋅ dl = ∫ J ⋅ ds = N ⋅
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theory itself is correct. The inacc
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( θ ) ⋅ g( θ, θ ) − H ( 0)
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where ( θ ) n A is the average of
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Since the definition of the mutual
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3Cs1 Cs1 − Cs1 − 3Cs1 6Cs1 4Cs1
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3.4.2 Mutual Inductances of the ABC
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where, ( θ ) n is the average of t
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1 0 α 1 − r 2π α − r 2π Fig
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When the skewing factor of the roto
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3.6 Calculation of Stator-Rotor Mut
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dλ v = R ⋅ i + (3.58) dt where,
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3.7.1.3 Stator flux linkage in ABC
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where, r R is the resistance matrix
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Only terms in equation (3.77) which
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119 ( ) ⎥ ⎥ ⎥ ⎥ ⎥ ⎥ ⎥
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−1 −1 −1 where, λ qdr = Tr L
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3.16 and Figure 3.17. It is found f
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Figure 3.11 The simulation of the d
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Figure 3.14 The simulation of the s
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Figure 3.16 Rotor bar currents duri
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Phase Y Figure 3.20 Air gap flux de
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Figure 3.24 Total air gap flux dens
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Figure 3.27 The air gap flux densit
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Figure 3.29 Air gap flux density co
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Figure 3.33 Air gap flux density in
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All the waveforms shown above are t
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Figure 3.39 Air gap flux density pr
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Figure 3.42 Normalized spectrum of
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CHAPTER 4 FULL MODEL SIMULATION OF
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Substituting (3.28) and (3.29) into
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Figure 4.3 Self-inductance under 20
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Figure 4.4 Mutual inductance under
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that L AB = L BA , L BC = L CB and
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the assumption that the rotor skew
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4.4 Mutual Inductances Calculation
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Figure 4.24 Stator rotor mutual ind
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Figure 4.25 Stator rotor mutual ind
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varying inductances excited by four
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Equations similar to (4.15-4.16) we
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the number of poles for the winding
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Figure 4.29 Dynamic response of dua
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(a) (b) (c) (d) Figure 4.32. Normal
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CHAPTER 5 FIELD ANALYSIS OF DUAL ST
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In the analysis that follows the fu
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where, C s1 is the number of series
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θ , ∂B1 µ 0r = ⋅ J1 θ ∂θ
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C C = k π ⋅ d s2 s2 s2 199 (5.19
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the XYZ winding set is obtained by
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u rpi 2π ' k − jk θ −( i−1)
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The corresponding flux densities in
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The first term in equation (5.55) i
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The second term in (5.64) is zero u
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5.2.2 Torque Equation The calculati
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Re j( ω ) ⎧ 1t− P1θ µ 0r j(
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* ( ) ( ) ( ) ⎛ P1 ⋅ ⋅ ⎞ j
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* Since both ( ) C 2π ∫ 0 2 * Cs
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(A) Induced voltage in the ABC wind
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5.3.3 Equation of Torque Contribute
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winding set works as a generator, w
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possible for the brushless doubly-f
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Since the number of rotor bar is n,
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5.6 Computer Simulation and Experim
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Figure 5.2. Simulation results for
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5.7. Conclusions In this chapter, u
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good steady-state predictions and c
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which are superimposed some space h
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(a) (b) (c) Figure 6.1: Main flux s
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(a) (b) (c) (d) (e) Figure 6.3: Fin
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(a) (b) Figure 6.5: Induced air-gap
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Substituting (6.7) into (6.4-6.6),
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L L L L L L L λ + lr1 m1 ls1 m1 lr
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6.4 Simulation and Experimental Res
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Figure 6.7 . Simulation results for
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Figure 6.9 Experimental results for
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diminish the contribution of the 6-
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CHAPTER 7 STEADY STATE ANALYSIS OF
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where, L L = (7.11) si mi iqdri λq
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Overall efficiency of the dual stat
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Figure 7.2 Stator current speed cha
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Figure 7.6 Power factor speed chara
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Figure 7.9 Power factor speed chara
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7.3.5 f = 35Hz and f = 90 Hz abc xy
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Figure 7.16 Torque speed characteri
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this conclusion is based on the ass
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Figure 7.21. ω s1 vs s2 ω when to
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Figure 7.25 ω s1 vs s2 ω when the
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Figure 7.28. Copper losses of the m
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7.4 Conclusions Based on the steady
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applications and possible use as st
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L pλ + λ = I − = σ (8.3) ( ω
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espectively. The stator q and d axi
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* 3 * ( V I ) V Re( M I ) 3 P p = R
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the modulation index of the rectifi
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Lie derivative and relative order d
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The above algorithm requires that t
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σ = 3 1+ K ( Vqs1iqs1 + Vds1 ds1)
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Butterworth polynomial with the den
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Table 8.1 Parameters of controllers
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generally the case to get a good pe
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Table 8.2 Machine parameters for si
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(a) (b) (c) (d) (e) (f) (g) Figure
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(a) (b) (c) (d) (e) (f) (g) (h) (i)
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(a) (b) (c) (d) (e) (f) (g) (h) (i)
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CHAPTER 9 HIGH PERFORMANCE CONTROL
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The qd0 voltage equations of a dual
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317 ( ) ( ) ( ) ( ) ( ) ⎥ ⎥ ⎥
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If the rotor speed and the rotor fl
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Infeasible region (a) Vdc1 and Vdc2
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The influences of the saturation of
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Figure 9.5(a), by varying the q-axi
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Figure 9.5 Steady state analysis, (
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L1 L3 2 ( 1− K ) Vdc1 3 = ( Vqs1i
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If the PI controllers are used and
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egulation capabilities of the contr
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(a) (b) (c) (d) (e) (f) (g) (h) (k)
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(a) (b) Figure 9.11. The starting p
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9.6 Conclusions The high performanc
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induction machine are applicable to
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In section 10.2, the fundamentals o
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The vector control of an induction
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possibilities for fault conditions,
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where, where, − r r L = (10.18) (
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qsi qsi * ( I I ) σ = K ⋅ − (1
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In the proposed control scheme, rot
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* ωr * ωr + + − ωr k p + ki s
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The value of ω 0 determines the dy
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10.4.4 Stator D-axis Current Contro
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(a) (b) (c) (d) (e) (f) Figure 10.4
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The proposed control scheme has als
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(a) (b) (c) (d) (e) (f) (g) Figure
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10.6 Full-order Flux Observer The c
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while the second three-phase windin
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L r L p ˆ λ ˆ ˆ (10.66) ri si r
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373 [ ] ( ) ( ) ( ) ( ) ( ) ( ) ( )
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t 2bi ⎛ rsiLri K iL ⎞ ⎛ ri K
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ri D i si ri ri si mi ri 2 ( K )
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esults show that the selected obser
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Figure 10.12 The poles of the 6-pol
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383 ( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )
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⎧t s ⎨ ⎩ts 1 2 = t = t 1 2 Th
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Figure 10.15 The poles of the machi
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X i i = X Y = Y i i ( σ , ω) ( σ
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this error is used as the feedback.
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ˆ ω rm The output error is expres
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The expressions of t1 i and t2 i ar
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397 ( ) ( ) ( ) bi ei i bi ei i ai
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The transfer function of rotor spee
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(a) (b) (c) (d) Figure 10.16 Pole-z
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Figure 10.19 Pole-zero maps with di
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Figure 10.22 Pole-zero maps with di
Page 447 and 448: should ensure the stability under a
Page 449 and 450: The boundary of the speed controlle
Page 451 and 452: 10.11 Simulation Results for Sensor
Page 453 and 454: Figure 10.28 Speed estimation for 2
Page 455 and 456: (a) (b) Figure 10.31 Speed estimati
Page 457 and 458: (a) (b) (c) (d) (e) (f) Figure 10.3
Page 459 and 460: Figure 10.34 Actual and estimated v
Page 461 and 462: CHAPTER 11 HARDWARE IMPLEMENTATION
Page 463 and 464: esistance for two phase windings. T
Page 465 and 466: 11.2.3 Short Circuit Test The short
Page 467 and 468: When the input voltages of 2-pole A
Page 469 and 470: winding set is generating and the o
Page 471 and 472: 11.4 Per Unit Model For the fixed p
Page 473 and 474: 1 = 12 2 0. 0024414 The transformat
Page 475 and 476: ase values of voltage/current. The
Page 477 and 478: Start System configuration Initiali
Page 479 and 480: CHAPTER 12 CONCLUSIONS AND FUTURE W
Page 481 and 482: Using the rotating-field theory and
Page 483 and 484: each winding have been clearly show
Page 485 and 486: voltages of different frequencies,
Page 487 and 488: REFERENCES 447
Page 489 and 490: [2.2]. P. C. Roberts, "A Study of B
Page 491 and 492: [5.3]. R. A. McMahon, P. C. Roberts
Page 493 and 494: [8.17]. O. Ojo, “Performance of s
Page 495 and 496: [10.5]. J. C. Moreira, K. T. Hung,
Page 497: [10.27]. M. Hinkkanen, “Analysis
Page 501 and 502: VITA Zhiqiao Wu was born in Shashi,
Page 503: 3. Zhiqiao Wu and O. Ojo, "High Per
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