Multi-Carrier and Spread Spectrum Systems: From OFDM and MC ...

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328 Additional Techniques for Capacity and Flexibility Enhancementboth curves shows the 3 dB array gain compared to the 1Tx scheme, which results fromthe coherent superposition of the signals from both Tx antennas. For the SPC schemean array gain of about 1.5 dB compared to the 1Tx scheme can be observed. SD cannotachieve an array gain compared to the SPC schemes. The array gain obtained with SPC isthe reason why SPC outperforms SD in channels with LOS, as shown in the next section.The BER versus SNR in the Ricean fading scenario (environment B) for a rate 1/2coded transmission is shown in Figure 6-30. SPC outperforms the 1Tx scheme as well asSD. EGT and MRT are shown as lower bounds. QEGT represents 1 bit quantized EGT.Figure 6-31 shows the corresponding results, where |H n (1) | and |H n(2) | are Rayleigh distributed(environment C). SPC requires a 0.6 dB higher SNR at a BER of 10 −4 comparedto SD. However, SPC requires less overheads for channel estimation compared to SDsince only one channel has to be estimated at the receiver.6.4.5.2 Effects of Channel EstimationThe system parameters are the same as in the previous section except for the channelestimation, which is no longer perfect. The filtering is performed by two-times onedimensionalWiener filtering (2 × 1D filtering) where for the filtering in each dimensionfive taps are used. The pilot spacing is six sub-carriers in the frequency direction and three10.10.011TxSDSPCQEGTEGTMRTBER0.0010.000110 −510 −6−2 −1 0 1 2 3 4 5 6SNR in dBFigure 6-30 BER versus SNR for SPC, SD, EGT, and MRT in a Ricean fading environment(environment B) with channel coding, = 0.9
Spatial Pre-Coding for Multi-Carrier Transmission 32910.10.011TxSDSPCQEGTEGTMRTBER0.0010.000110 −510 −60 1 2 3 4 5 6 7 8SNR in dBFigure 6-31 BER versus SNR for SPC, SD, EGT, and MRT in a Rayleigh fading environment(environment C) with channel coding, = 0.8OFDM symbols in the time direction. As a propagation channel the COST 207 typicalurban (TU) channel model is taken. The maximum velocity of the mobile user is 30 km/h,which corresponds to a Doppler frequency of 55.6 Hz. A classical Doppler spectrum isassumed.In Figure 6-32 the BER versus SNR for the spatial pre-coding schemes with channelestimation errors based on a two-dimensional channel estimation are shown. The sametotal pilot power is assigned to each scheme. The pre-coding schemes MRT, EGT, andSD need to estimate two channels at the receiver. Since SPC and 1Tx have to estimateonly one channel, they have twice the pilot power available for channel estimation perchannel compared to MRT, EGT, and SD. The channel estimation accuracy for MRT,EGT, and SD degrades compared to the accuracy with SPC and 1Tx. It can be observedthat, when taking imperfection due to channel estimation into account, the low complexSPC scheme outperforms SD and EGT and performs similar as the optimum MRT schemeat BERs ≤ 10 −4 [17].6.4.5.3 Effects of SpreadingFor spreading, Walsh–Hadamard codes of length L = 8 are used and eight data symbolsare superimposed, i.e. code division multiplexing (CDM) is applied. For data detection
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Multi-Carrier andSpread SpectrumSys
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This edition first published 2008©
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Contentsix4.3.2 One-Dimensional Cha
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ForewordThis book discusses multi-c
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Preface (First Edition)Nowadays, mu
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AcknowledgementsThe authors would l
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2 Introductionambitious technologic
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4 IntroductionTables 1 and 2 summar
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6 IntroductionPower densityTimeFreq
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8 Introductiona high immunity again
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10 Introductionprocessing gain P G
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12 Introductionand interactive mult
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14 Introduction[43] Saltzberg, B. R
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16 FundamentalsBSTSFigure 1-1Time-v
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18 Fundamentalswhere p =|a p | 2 (1
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20 Fundamentalssuch that the effect
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22 FundamentalsTable 1-2 Delay powe
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24 Fundamentals(i) Fixed Positioned
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26 Fundamentalson sub-channel n of
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28 Fundamentals10 010 −1OFDM (OFD
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30 Fundamentalsin order to achieve
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32 FundamentalsThe discrete length
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34 FundamentalsThe following matrix
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36 FundamentalsTable 1-11Wireless l
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38 FundamentalsFrequency hopping (F
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40 FundamentalsFinally, a threshold
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42 Fundamentals1.3.3 Applications o
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44 FundamentalsTable 1-12Radio link
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46 FundamentalsOrthogonalV-SF codeF
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{{48 Fundamentalsdata symbolsspread
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50 FundamentalsCellular Mobile Radi
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52 Fundamentals[27] Haindl B., “M
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2MC-CDMA and MC-DS-CDMAIn this chap
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MC-CDMA 57whered = (d (0) ,d (1) ,.
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MC-CDMA 59i.e. the spreading is per
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MC-CDMA 61Table 2-1 PAPR bounds of
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MC-CDMA 632.1.4.4 Rotated Constella
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MC-CDMA 65After inverse OFDM the re
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MC-CDMA 67and requires only informa
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MC-CDMA 69hard interference evaluat
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MC-CDMA 71Thedataofthedesireduserk
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MC-CDMA 73L corresponds to the spre
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MC-CDMA 752.1.7 Combined Equalizati
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MC-CDMA 77broadcasting, WLAN, and W
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MC-CDMA 792.1.8.1 Log-Likelihood Ra
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MC-CDMA 81For coded MC-CDMA systems
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MC-CDMA 83where Q different user gr
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MC-CDMA 85Table 2-2MC-CDMA system p
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MC-CDMA 87first iteration. The opti
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MC-CDMA 8910 010 −110 −2BER10
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MC-CDMA 9110 010 −1BER10 −210
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MC-CDMA 9310 010 −110 −2BER10
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MC-DS-CDMA 95c (k) (t)f 00d (k)S/P+
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MC-DS-CDMA 97The user-specific dela
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MC-DS-CDMA 9910 010 −1BER10 −21
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References 101[7] Brüninghaus K. a
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References 103[49] Steiner B., “U
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106 Hybrid Multiple Access SchemesI
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108 Hybrid Multiple Access Schemesw
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110 Hybrid Multiple Access Schemest
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112 Hybrid Multiple Access SchemesO
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114 Hybrid Multiple Access SchemesT
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116 Hybrid Multiple Access SchemesA
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120 Hybrid Multiple Access Schemest
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122 Hybrid Multiple Access SchemesA
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126 Hybrid Multiple Access Schemes[
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4Implementation IssuesA general PHY
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Multi-Carrier Modulation and Demodu
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Synchronization 139The performance
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Synchronization 141null symbol as a
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Synchronization 143resulting SNR ca
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Synchronization 145SNR Degradation
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Synchronization 147FFTr(k)estimated
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Synchronization 149the timing error
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Synchronization 151A first simple s
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Synchronization 153Transmitted 2 re
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Channel Estimation 155Special cases
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Channel Estimation 157The mean squa
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Channel Estimation 159by the second
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Channel Estimation 161Given the nor
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Channel Estimation 163and f D, filt
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Channel Estimation 16510 010 −110
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Channel Estimation 16710 010 −13
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Channel Estimation 169in order to r
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Channel Estimation 17110 010 −1BU
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Channel Estimation 173timefreq. 00
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Channel Coding and Decoding 1754.4.
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Channel Coding and Decoding 177Tabl
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Channel Coding and Decoding 179a (k
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Channel Coding and Decoding 181n rk
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Channel Coding and Decoding 183Bit
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Channel Coding and Decoding 185Bit
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Signal Constellation, Mapping, De-M
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Signal Constellation, Mapping, De-M
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Adaptive Techniques in Multi-Carrie
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RF Issues 193hence reduce, for inst
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RF Issues 195s(t)r(t)e jf(t)White n
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RF Issues 197receivedsignalto detec
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RF Issues 1994.7.2.1 Effects of Non
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RF Issues 2011e−011e−02UplinkDo
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RF Issues 203of data pre-distortion
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RF Issues 205Table 4-8Minimum total
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RF Issues 207Detection strategyIn t
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RF Issues 209above formula becomes(
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References 211[21] Fazel K., “Nar
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References 213[66] Nobilet S., Hela
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5Applications5.1 IntroductionThe de
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Introduction 217high speed as well
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3GPP Long Term Evolution (LTE) 219H
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3GPP Long Term Evolution (LTE) 221U
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3GPP Long Term Evolution (LTE) 2231
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3GPP Long Term Evolution (LTE) 227T
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3GPP Long Term Evolution (LTE) 229C
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WiMAX 237Table 5-12 Downlink LTE sp
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WiMAX 239Wi-FiBusinessTSWiMAX BSTSM
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WiMAX 241Table 5-16Summary of the I
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WiMAX 243WiMAXInteroperabilityInter
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WiMAX 245UNIAirinterfaceSNITerminal
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WiMAX 247Radio ResourceControlIniti
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WiMAX 249Frame n−1 Frame n Frame
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WiMAX 251Read RF-Channel ListScan F
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WiMAX 253NormaloperationTS measures
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WiMAX 255Table 5-18Example of some
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WiMAX 257Total bandwidth (between 1
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WiMAX 259Sub-carriers (frequency)n0
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ApplicationsWiMAX 261Table 5-23 Gen
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WiMAX 263Table 5-27(OFDMA)FEC codin
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WiMAX 265M-QAMMappingSTC withSpatia
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WiMAX 267Frame n−1 Frame n Frame
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WiMAX 269Table 5-29WirelessMAN-OFDM
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WiMAX 2710Power density in dB−25
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WiMAX 273Table 5-37diversityPeak da
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WiMAX 275Table 5-41DL link budget e
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Page 317 and 318: References 297Table 5-58Parameters
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Page 373 and 374: Index3GPP 218Adaptive techniques 19
Page 375 and 376: Index 355Forward error correction (
Page 377 and 378: Index 357Multi-carrier modulation a
Page 379 and 380: Index 359Maximum likelihood paramet
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