Radio Frequency Integrated Circuit Design - Webs

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LNA Design With any of these mirrors, a voltage at the collector of N � Q 1 must be maintained above a minimum level or else the transistor will go into saturation. Saturation will lead to bad matching and nonlinearity. 6.7.1 Temperature Effects For transistor current given by 189 VBE iC ≈ IS e vT (6.103) the temperature affects parameters such as IS and V BE. Also, current gain � is affected by temperature. IS doubles for every 10°C rise in temperature, while the relationship for V BE and � with temperature is shown in (6.104) and (6.105). �V BE �T | ≈−2 mV/°C (6.104) iC = constant �� T ≈+0.5%/°C (6.105) A typical temperature range for an integrated circuit might be 0 to 85°C. Thus, for a constant voltage bias, if the current is 1 mA at 20°C, then it will change to 0.2 mA at 0°C and to 1.65 mA at 85°C. Thus, the current changes by more than eight times over this temperature range. This illustrates why constant current biasing (for example, with the current mirrors discussed in Section 6.7) is used. If both transistors in the current mirror are at the same temperature, then output current is roughly independent of temperature. 6.8 Broadband LNA Design Example As a final major design example, we will design a broadband LNA to work from 50 to 900 MHz and with input matched to 75� with an S11 better than −10 dB over this range. The gain must be more than 12 dB, noise figure less than 5 dB, and the IIP3 must be greater than 6 dBm. The circuit must operate with a 3.3V supply and consume no more than 8 mA of current. Assume that there is a suitable 50-GHz process available for this design. Assume that the LNA will drive an on-chip mixer with an input impedance of 5 k�. This is going to be a high-linearity part and it needs to be broadband. Therefore, the matching and the load cannot make use of reactive components.
190 Radio Frequency Integrated Circuit Design This means that, of the designs presented so far, an LNA with shunt feedback will have to be used. This can be combined with a common-base amplifier to provide better frequency response and an output buffer to avoid the problem of loading the circuit. A first cut at a topology that could satisfy the requirements is shown in Figure 6.37. Note that emitter degeneration has been added to this circuit. Degeneration will almost certainly be required due to the linearity requirement. We have left the current source as ideal for this example. Also, we are not including the bias circuitry that will be needed at the base of Q 1. The first specification we will satisfy is the requirement of 8-mA total supply current. It may even be possible to do this design with less current. The trade-off is that as the current is decreased, R E must be increased to deliver the same linearity, and this will affect noise. We will begin this design using all the allowed current, and at the end, we will consider the possibility of reducing the current in a second iteration. The total current must be divided between the two stages of this amplifier. The buffer must have enough current so that it continues to operate properly even when it has to deliver a lot of current in the presence of large signals. Since the load resistance is large, the buffer will have to drive an effective resistance of approximately R f + 75�. This is expected to be a few hundred ohms and will require several hundreds of microamps of ac current. We will start with 3 mA in the buffer and 5 mA in the driver stage. We can now start to size the resistors and capacitor in the circuit by considering linearity. An IIP3 of 6 dBm in a 75� system, assuming that the input is matched, means that the IIP3 in terms of voltage will be 546 mVrms. Since we have assumed a current of 5 mA in the driver, we can now use (6.85) to determine the size of R E : Figure 6.37 Broadband LNA sample circuit.
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Radio Frequency Integrated Circuit
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Radio Frequency Integrated Circuit
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Contents Foreword xv Acknowledgment
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Contents 3.8 Base Shot Noise Discus
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Contents 5.25 Packaging 135 5.25.1
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Contents 7.12 General Design Commen
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Contents 9.5 Some Simple Image Reje
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Foreword I enjoyed reading this boo
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Foreword estimates of parasitic cap
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xx Radio Frequency Integrated Circu
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2 Radio Frequency Integrated Circui
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2 Issues in RFIC Design, Noise, Lin
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Issues in RFIC Design, Noise, Linea
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The input noise is Issues in RFIC D
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2.5 Filtering Issues Issues in RFIC
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3 A Brief Review of Technology 3.1
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A Brief Review of Technology IC = I
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3.4 Small-Signal Model A Brief Revi
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3.6 High-Frequency Effects A Brief
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A Brief Review of Technology If thi
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A Brief Review of Technology Soluti
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A Brief Review of Technology 3.8 Ba
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A Brief Review of Technology • Pi
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A Brief Review of Technology 3.16,
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A Brief Review of Technology The tr
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4 Impedance Matching 4.1 Introducti
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Impedance Matching Z 2 = Z in + j
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Figure 4.5 A Smith chart. Impedance
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4.3 Impedance Matching Impedance Ma
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Impedance Matching Figure 4.9 Which
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Impedance Matching Figure 4.11 Lowp
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Impedance Matching section, convers
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Impedance Matching Much as in the p
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Impedance Matching Note that dots i
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Impedance Matching Thus, in the fir
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Impedance Matching The exact resist
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Impedance Matching 4.10 Quality Fac
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Impedance Matching Example 4.7 Matc
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Impedance Matching line to change w
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Impedance Matching S22 = b 2 a2 | a
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Impedance Matching without the need
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96 Radio Frequency Integrated Circu
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98 Radio Frequency Integrated Circu
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100 Radio Frequency Integrated Circ
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Voltage-Controlled Oscillators back
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I C_AVE = 1 Voltage-Controlled Osci
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Voltage-Controlled Oscillators Loop
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Voltage-Controlled Oscillators freq
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Voltage-Controlled Oscillators Figu
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Voltage-Controlled Oscillators from
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Voltage-Controlled Oscillators [10]
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10 Power Amplifiers 10.1 Introducti
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Power Amplifiers where G is the pow
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Power Amplifiers Figure 10.4 Optima
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Power Amplifiers Figure 10.8 Power
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Power Amplifiers Figure 10.9 Curren
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Power Amplifiers The efficiency is
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Power Amplifiers sinusoid), this pe
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Power Amplifiers Note that this agr
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Power Amplifiers stabilization. The
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Power Amplifiers Solution The first
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Power Amplifiers Figure 10.22 Class
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Figure 10.24 Class E waveforms. Pow
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Power Amplifiers B = 0.1836 0.81Q R
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Power Amplifiers Figure 10.25 Initi
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Power Amplifiers added to the funda
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Power Amplifiers 10.8.1 Variation o
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Example 10.4 Class F Power Amplifie
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Figure 10.36 Class H amplifier. Pow
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Power Amplifiers ered quite good. O
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Power Amplifiers Figure 10.39 Time-
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Figure 10.42 High-Q matching circui
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Figure 10.44 Multiple transistors.
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Power Amplifiers Figure 10.48 Combi
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Power Amplifiers have very narrow b
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Power Amplifiers Figure 10.53 Feedf
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Power Amplifiers in class A (input
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About the Authors John Rogers recei
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Index 1-dB compression point, 30-32
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Index Damped resonator, 247-48 Emit
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Index Local oscillator, 5 Mixing co
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Index Quadrature phase shift keying
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