Radio Frequency Integrated Circuit Design - Webs

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Mixers Figure 7.8 Downconversion frequency domain plot. a slightly modified definition of noise figure is used. Noise factor for a mixer is defined as F = Notot(� IF ) No(source)(� IF ) 207 (7.21) where Notot(� IF ) is the total output noise at the IF and No(source)(� IF )isthe output noise at the IF due to the source. The source and all circuit elements generate noise at all frequencies, and many of these frequencies will produce noise at the output IF due to the mixing action of the circuit. Usually the two dominant frequencies are the input frequency and the image frequency. To make things even more complicated, single-sideband (SSB) noise figure or double-sideband (DSB) noise figure is defined. The difference between the two definitions is the value of the denominator in (7.21). In the case of doublesideband noise figure, all the noise due to the source at the output frequency is considered (noise of the source at the input and image frequencies). In the case of single-sideband noise figure, only the noise at the output frequency due to the source that originated at the RF frequency is considered. Thus, using the single-sideband noise figure definition, even an ideal noiseless mixer would have a noise figure of 3 dB. This is because the noise of the source would be doubled in the output due to the mixing of both the RF and image frequency noise to the intermediate frequency. Thus, it can be seen that and No(source)DSB = No(source)SSB + 3 dB (7.22) NFDSB = NFSSB − 3 dB (7.23)
208 Radio Frequency Integrated Circuit Design This is not quite correct, since an input filter will also affect the output noise, but this rule is usually used. Usually, single-sideband noise figure is used for a mixer in a superheterodyne radio receiver, since an image reject filter preceding the mixer removes noise from the image. Largely because of the added complexity and the presence of noise that is frequency translated, mixers tend to be much noisier than LNAs. The differential pair that forms the bottom of the mixer represents an unattainable lower bound on the noise figure of the mixer itself. Mixer noise will always be higher because noise sources in the circuit get translated to different frequencies and this often ‘‘folds’’ noise into the output frequency. Generally, mixers have three frequency bands where noise is important: 1. Noise already present at the IF: The transistors and resistors in the circuit will generate noise at the IF. Some of this noise will make it to the output and corrupt the signal. For example, the collector resistors will add noise directly at the output IF. 2. Noise at the RF and image frequency: Any noise present at the RF and image frequency will also be mixed down to the IF. For instance, the collector shot noise of Q 1 at the RF and at the image frequency will both appear at the IF at the output. 3. Noise at multiples of the LO frequencies: Any noise that is near a multiple of the LO frequency can also be mixed down to the IF, just like the noise at the RF. Also note that noise over a cycle of the LO is not constant, as illustrated in Figure 7.9. At large negative or positive voltage on the LO, dominant noise comes from the bottom transistors. This is the expected behavior, as the LO is causing the upper quad transistors to be switched between cutoff and saturation. In both of these two states, the transistors will add very little noise because they have no gain. We also note that gain from the RF input is maximum when the upper quad transistors are fully switched one way or the other. Thus, a large LO signal that switches rapidly between the two states is ideal to maximize the signal-to-noise ratio. However, for the finite rise and fall time in the case of a square wave LO signal, or for a sinusoidal LO voltage, the LO voltage will go through zero. During this time, these transistors will be on and in the active region. Thus, in this region they behave like an amplifier and will cause noise in the LO and in the upper quad transistors to be amplified and passed on to the output. As shown in Figure 7.9, for LO voltages near zero, noise due to the upper quad transistors is dominant. At the same time, in this region, gain from the RF is very low; thus for small LO voltages, the signal-to-noise ratio is very poor, so time spent in this region should be minimized.
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Radio Frequency Integrated Circuit
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Radio Frequency Integrated Circuit
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Contents Foreword xv Acknowledgment
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Contents 3.8 Base Shot Noise Discus
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Contents 5.25 Packaging 135 5.25.1
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Contents 7.12 General Design Commen
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Contents 9.5 Some Simple Image Reje
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Foreword I enjoyed reading this boo
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Foreword estimates of parasitic cap
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xx Radio Frequency Integrated Circu
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2 Radio Frequency Integrated Circui
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2 Issues in RFIC Design, Noise, Lin
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Issues in RFIC Design, Noise, Linea
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The input noise is Issues in RFIC D
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2.5 Filtering Issues Issues in RFIC
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3 A Brief Review of Technology 3.1
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A Brief Review of Technology IC = I
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3.4 Small-Signal Model A Brief Revi
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3.6 High-Frequency Effects A Brief
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A Brief Review of Technology If thi
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A Brief Review of Technology Soluti
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A Brief Review of Technology 3.8 Ba
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A Brief Review of Technology • Pi
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A Brief Review of Technology 3.16,
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A Brief Review of Technology The tr
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4 Impedance Matching 4.1 Introducti
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Impedance Matching Z 2 = Z in + j
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Figure 4.5 A Smith chart. Impedance
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4.3 Impedance Matching Impedance Ma
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Impedance Matching Figure 4.9 Which
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Impedance Matching Figure 4.11 Lowp
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Impedance Matching section, convers
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Impedance Matching Much as in the p
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Impedance Matching Note that dots i
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Impedance Matching Thus, in the fir
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Impedance Matching The exact resist
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Impedance Matching 4.10 Quality Fac
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Impedance Matching Example 4.7 Matc
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Impedance Matching line to change w
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Impedance Matching S22 = b 2 a2 | a
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Impedance Matching without the need
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96 Radio Frequency Integrated Circu
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98 Radio Frequency Integrated Circu
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100 Radio Frequency Integrated Circ
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Voltage-Controlled Oscillators back
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I C_AVE = 1 Voltage-Controlled Osci
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Voltage-Controlled Oscillators Loop
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Voltage-Controlled Oscillators freq
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Voltage-Controlled Oscillators Figu
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Voltage-Controlled Oscillators from
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Voltage-Controlled Oscillators [10]
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10 Power Amplifiers 10.1 Introducti
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Power Amplifiers where G is the pow
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Power Amplifiers Figure 10.4 Optima
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Power Amplifiers Figure 10.8 Power
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Power Amplifiers Figure 10.9 Curren
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Power Amplifiers The efficiency is
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Power Amplifiers sinusoid), this pe
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Power Amplifiers Note that this agr
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Power Amplifiers stabilization. The
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Power Amplifiers Solution The first
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Power Amplifiers Figure 10.22 Class
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Figure 10.24 Class E waveforms. Pow
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Power Amplifiers B = 0.1836 0.81Q R
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Power Amplifiers Figure 10.25 Initi
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Power Amplifiers added to the funda
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Power Amplifiers 10.8.1 Variation o
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Example 10.4 Class F Power Amplifie
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Figure 10.36 Class H amplifier. Pow
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Power Amplifiers ered quite good. O
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Power Amplifiers Figure 10.39 Time-
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Figure 10.42 High-Q matching circui
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Figure 10.44 Multiple transistors.
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Power Amplifiers Figure 10.48 Combi
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Power Amplifiers have very narrow b
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Power Amplifiers Figure 10.53 Feedf
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Power Amplifiers in class A (input
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About the Authors John Rogers recei
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Index 1-dB compression point, 30-32
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Index Damped resonator, 247-48 Emit
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Index Local oscillator, 5 Mixing co
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Index Quadrature phase shift keying
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