Radio Frequency Integrated Circuit Design - Webs

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Mixers Figure 7.13 Mixer for noise analysis and transistor noise model. Table 7.1 Mixer Noise and Dominant Sources of Noise Differential Output Voltage at � IF Input at Input at Input at Input at Total Source � IF � RF 2� LO − � IF 3� LO − � IF V 2 × 10 −6 (R SR ) (0.7 nV) (0.72 mV) (0.2 nV) (0.11 mV) (1.08) Bottom 0.9 nV 1.77 mV 4.0 nV 0.29 mV 6.44 vrbquad 0.25 mV 0.03 mV 0.20 mV 0.02 mV 0.15 i cquad 0.26 mV 0.15 mV 1.5 � V 0.03 mV 1.17 i bquad 36 nV 0.13 mV 25 nV 0.03 mV 0.04 v RL 1.77 mV 16 nV 4.4 � V 1.3 nV 3.13 Freq. bands 1 2 2 2 10.93 213
214 Radio Frequency Integrated Circuit Design Table 7.2 Breakdown of Noise in the RF Stage Source Noise Out V 2 r b,Q1, 2 r e,Q1, 2 i b i c Total Q 1,2 0.51 × 10 −6 0.08 × 10 −6 0.06 × 10 −6 1.21 × 10 −6 1.86 × 10 −6 Source Noise Out V 2 R SR 1.08 × 10 −6 R BB 1.08 × 10 −6 R BE 0.20 × 10 −6 R E 2.22 × 10 −6 Total 6.44 × 10 −6 equal input at the image frequency. Thus, for an input at the RF or around other harmonics of the LO frequency, the multiplier is 2, while for noise inputs at the IF, the multiplier is 1. Different frequencies are dominant for different parts of the mixer. For the bottom circuitry, the most important input frequency is the RF (and image frequency). For the load resistor, the only important component occurs at the IF, while for the quad switching transistors, both the RF and IF are important. Generally, noise around the LO second harmonic or higher harmonics is not important; however, the third harmonic will add a bit of noise from the bottom circuitry. As for sources of noise, the bottom circuitry is seen to be the dominant factor (true only if the LO amplitude is large enough to switch the quad transistors fully). Thus, to minimize noise, the RF input stage must be optimized, similar to that of an LNA design. Of the bottom noise sources, degeneration can quickly become the dominant noise source for high-linearity design. If linearity allows, it is possible to use inductor degeneration for optimal noise and power matching. Also, in this example, bias resistors contributed significantly to the noise. In an inductively degenerated mixer, bias resistors can be made significantly larger to minimize the noise contribution from them. Double-sideband noise figure can be calculated as follows: DSB noise figure = 10 log10� 10.93 = 10.1 dB 1.08� Minimum noise figure from the RF stage can be calculated as DSB NFmin = 10 log10� 6.44 = 7.75 1.08� Note that single-sideband noise figure would consider source noise in the RF band only; thus, noise figure would have been higher by about 3 dB.
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Radio Frequency Integrated Circuit
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Radio Frequency Integrated Circuit
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Contents Foreword xv Acknowledgment
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Contents 3.8 Base Shot Noise Discus
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Contents 5.25 Packaging 135 5.25.1
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Contents 7.12 General Design Commen
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Contents 9.5 Some Simple Image Reje
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Foreword I enjoyed reading this boo
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Foreword estimates of parasitic cap
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xx Radio Frequency Integrated Circu
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2 Radio Frequency Integrated Circui
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2 Issues in RFIC Design, Noise, Lin
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Issues in RFIC Design, Noise, Linea
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The input noise is Issues in RFIC D
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2.5 Filtering Issues Issues in RFIC
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3 A Brief Review of Technology 3.1
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A Brief Review of Technology IC = I
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3.4 Small-Signal Model A Brief Revi
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3.6 High-Frequency Effects A Brief
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A Brief Review of Technology If thi
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A Brief Review of Technology Soluti
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A Brief Review of Technology 3.8 Ba
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A Brief Review of Technology • Pi
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A Brief Review of Technology 3.16,
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A Brief Review of Technology The tr
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4 Impedance Matching 4.1 Introducti
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Impedance Matching Z 2 = Z in + j
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Figure 4.5 A Smith chart. Impedance
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4.3 Impedance Matching Impedance Ma
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Impedance Matching Figure 4.9 Which
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Impedance Matching Figure 4.11 Lowp
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Impedance Matching section, convers
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Impedance Matching Much as in the p
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Impedance Matching Note that dots i
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Impedance Matching Thus, in the fir
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Impedance Matching The exact resist
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Impedance Matching 4.10 Quality Fac
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Impedance Matching Example 4.7 Matc
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Impedance Matching line to change w
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Impedance Matching S22 = b 2 a2 | a
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Impedance Matching without the need
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96 Radio Frequency Integrated Circu
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98 Radio Frequency Integrated Circu
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100 Radio Frequency Integrated Circ
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Voltage-Controlled Oscillators back
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I C_AVE = 1 Voltage-Controlled Osci
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Voltage-Controlled Oscillators Loop
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Voltage-Controlled Oscillators freq
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Voltage-Controlled Oscillators Figu
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Voltage-Controlled Oscillators from
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Voltage-Controlled Oscillators [10]
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10 Power Amplifiers 10.1 Introducti
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Power Amplifiers where G is the pow
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Power Amplifiers Figure 10.4 Optima
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Power Amplifiers Figure 10.8 Power
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Power Amplifiers Figure 10.9 Curren
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Power Amplifiers The efficiency is
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Power Amplifiers sinusoid), this pe
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Power Amplifiers Note that this agr
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Power Amplifiers stabilization. The
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Power Amplifiers Solution The first
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Power Amplifiers Figure 10.22 Class
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Figure 10.24 Class E waveforms. Pow
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Power Amplifiers B = 0.1836 0.81Q R
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Power Amplifiers Figure 10.25 Initi
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Power Amplifiers added to the funda
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Power Amplifiers 10.8.1 Variation o
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Example 10.4 Class F Power Amplifie
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Figure 10.36 Class H amplifier. Pow
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Power Amplifiers ered quite good. O
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Power Amplifiers Figure 10.39 Time-
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Figure 10.42 High-Q matching circui
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Figure 10.44 Multiple transistors.
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Power Amplifiers Figure 10.48 Combi
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Power Amplifiers have very narrow b
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Power Amplifiers Figure 10.53 Feedf
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Power Amplifiers in class A (input
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About the Authors John Rogers recei
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Index 1-dB compression point, 30-32
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Index Damped resonator, 247-48 Emit
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Index Local oscillator, 5 Mixing co
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Index Quadrature phase shift keying
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