Radio Frequency Integrated Circuit Design - Webs

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Voltage-Controlled Oscillators Figure 8.32 Short tail pair with a large sinusoidal voltage applied to the base. It can be shown, provided V tank/vT > 8 (which is reasonable for most practical oscillator amplitudes), that i fund Itank = 2 � 281 (8.67) Thus, if the parallel resistance of the resonator is R p , the peak voltage developed across the resonator differentially will be given by V tank = i fundRp = 2 �� 2 � Itank� � R p = 2 � ItankRp (8.68) Note that there are two currents of the type described in (8.67), one for each transistor. However, the current flows down through the supply, so only develops a voltage across half the parallel resonator resistance. The case where the current source in Figure 8.32 is made from a resistor is slightly more complicated. The total current flowing through the oscillator will change over a cycle (with minimum current at the zero crossings and maximum current at the voltage peaks). Equation (8.65) can be modified to take into account the resistor. ic (� ) ≈ V B + | V tank cos (� ) 2 R bias V tank v cos (� ) 1 + e T | − VBEQ = I BQ + |V tank cos (� )| 2R bias V tank v cos (� ) 1 + e T (8.69)
282 Radio Frequency Integrated Circuit Design where R bias is the tail resistor that is serving as a current source, I BQ is the quiescent bias current before oscillations begin, and VBEQ is the quiescent base emitter voltage of Q 1 or Q 2. It is assumed that VBEQ is constant in this expression, which is a good approximation for the half cycle when the transistor is on. In the other half cycle, the denominator will force the expression to zero for any reasonable value of V tank (V tank >> v T ), so the approximation will not seriously affect the shape of the resulting waveform. This expression can be used to find the average dc operating current in the circuit (which will be higher than the quiescent current). This current also depends on the final amplitude of the VCO. 2� I AVE = 1 2� � 0 I BQ + |V tank cos (� )| 2R bias V tank v cos (� ) 1 + e T d� ≈ I BQ + V tank �R bias (8.70) The fundamental component of the current can also be extracted from (8.69) as before. i fund = 2 � � � �IBQ + 0 |Vtank cos (� )| 2R bias V tank 1 + e v T cos (� ) �cos (� ) d� ≈ 2 � I BQ + V tank 4R bias (8.71) This allows us to determine the ratio of current at the fundamental to average current: k = i fund = I AVE 2 � I BQ + V tank 4R bias I BQ + V tank �Rbias (8.72) In the limit of large and small V tank, it can be seen that k is bounded by 2 � ≤ k ≤ � 4 (8.73) Therefore, the oscillation amplitude can once again be given in terms of dc current as
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Radio Frequency Integrated Circuit
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Radio Frequency Integrated Circuit
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Contents Foreword xv Acknowledgment
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Contents 3.8 Base Shot Noise Discus
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Contents 5.25 Packaging 135 5.25.1
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Contents 7.12 General Design Commen
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Contents 9.5 Some Simple Image Reje
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Foreword I enjoyed reading this boo
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Foreword estimates of parasitic cap
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xx Radio Frequency Integrated Circu
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2 Radio Frequency Integrated Circui
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2 Issues in RFIC Design, Noise, Lin
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Issues in RFIC Design, Noise, Linea
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The input noise is Issues in RFIC D
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2.5 Filtering Issues Issues in RFIC
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3 A Brief Review of Technology 3.1
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A Brief Review of Technology IC = I
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3.4 Small-Signal Model A Brief Revi
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3.6 High-Frequency Effects A Brief
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A Brief Review of Technology If thi
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A Brief Review of Technology Soluti
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A Brief Review of Technology 3.8 Ba
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A Brief Review of Technology • Pi
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A Brief Review of Technology 3.16,
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A Brief Review of Technology The tr
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4 Impedance Matching 4.1 Introducti
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Impedance Matching Z 2 = Z in + j
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Figure 4.5 A Smith chart. Impedance
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4.3 Impedance Matching Impedance Ma
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Impedance Matching Figure 4.9 Which
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Impedance Matching Figure 4.11 Lowp
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Impedance Matching section, convers
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Impedance Matching Much as in the p
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Impedance Matching Note that dots i
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Impedance Matching Thus, in the fir
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Impedance Matching The exact resist
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Impedance Matching 4.10 Quality Fac
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Impedance Matching Example 4.7 Matc
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Impedance Matching line to change w
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Impedance Matching S22 = b 2 a2 | a
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Impedance Matching without the need
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96 Radio Frequency Integrated Circu
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98 Radio Frequency Integrated Circu
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100 Radio Frequency Integrated Circ
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Page 326 and 327: Voltage-Controlled Oscillators back
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10 Power Amplifiers 10.1 Introducti
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Power Amplifiers where G is the pow
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Power Amplifiers Figure 10.4 Optima
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Power Amplifiers Figure 10.8 Power
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Power Amplifiers Figure 10.9 Curren
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Power Amplifiers The efficiency is
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Power Amplifiers sinusoid), this pe
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Power Amplifiers Note that this agr
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Power Amplifiers stabilization. The
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Power Amplifiers Solution The first
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Power Amplifiers Figure 10.22 Class
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Figure 10.24 Class E waveforms. Pow
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Power Amplifiers B = 0.1836 0.81Q R
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Power Amplifiers Figure 10.25 Initi
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Power Amplifiers added to the funda
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Power Amplifiers 10.8.1 Variation o
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Example 10.4 Class F Power Amplifie
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Figure 10.36 Class H amplifier. Pow
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Power Amplifiers ered quite good. O
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Power Amplifiers Figure 10.39 Time-
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Figure 10.42 High-Q matching circui
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Figure 10.44 Multiple transistors.
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Power Amplifiers Figure 10.48 Combi
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Power Amplifiers have very narrow b
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Power Amplifiers Figure 10.53 Feedf
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Power Amplifiers in class A (input
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About the Authors John Rogers recei
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Index 1-dB compression point, 30-32
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Index Damped resonator, 247-48 Emit
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Index Local oscillator, 5 Mixing co
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Index Quadrature phase shift keying
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